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NCP3065, NCV3065 Up to 1.5 A Constant Current Switching Regulator for LEDs
The NCP3065 is a monolithic switching regulator designed to deliver constant current for powering high brightness LEDs. The device has a very low feedback voltage of 235 mV (nominal) which is used to regulate the average current of the LED string. In addition, the NCP3065 has a wide input voltage up to 40 V to allow it to operate from 12 Vac or 12 Vdc supplies commonly used for lighting applications as well as unregulated supplies such as Lead Acid batteries. The device can be configured in a controller topology with the addition of an external transistor to support higher LED currents beyond the 1.5 A rated switch current of the internal transistor. The NCP3065 switching regulator can be configured in Step-Down (Buck) and Step-Up (boost) topologies with a minimum number of external components.
Features http://onsemi.com MARKING DIAGRAMS
8 1 SOIC-8 D SUFFIX CASE 751 3065 ALYWG G 1
* * * * * * * * * * * * * *
Integrated 1.5 A Switch Input Voltage Range from 3.0 V to 40 V Low Feedback Voltage of 235 mV Cycle-by-Cycle Current Limit No Control Loop Compensation Required Frequency of Operation Adjustable up to 250 kHz Operation with All Ceramic Output Capacitors or No Output Capacitance Analog and Digital PWM Dimming Capability Internal Thermal Shutdown with Hysteresis Automotive Version Available Automotive and Marine Lighting High Power LED Driver Constant Current Source Low Voltage LED Lighting (Landscape, Path, Solar, MR16 Replacement)
+LED
Rs
8
1
NCP3065 AWL YYWWG
PDIP-8 P, P1 SUFFIX CASE 626
8 1 DFN-8 MN SUFFIX CASE 488 NCP3065 A L, WL Y, YY W, WW G or G = = = = = = 3065 ALYW G G
Applications
Specific Device Code Assembly Location Wafer Lot Year Work Week Pb-Free Package
(Note: Microdot may be in either location) D
0.15 W Vin
NCP3065 NC SWC Ipk SWE CT Vin FB GND Vth = 0.235 V Cin 220 mF CT 2.2 nF R D
L LED Cluster
ORDERING INFORMATION
See detailed ordering and shipping information in the package dimensions section on page 15 of this data sheet.
Cout 22 mF
D -LED Rsense 0.68 W
Figure 1. Typical Buck Application Circuit
(c) Semiconductor Components Industries, LLC, 2007
1
July, 2007 - Rev. 0
Publication Order Number: NCP3065/D
NCP3065, NCV3065
Switch Collector Switch Emitter
Switch Emitter Timing Capacitor GND
2 3 4 (Top View)
7 6 5
Ipk Sense VCC Comparator Inverting Input
EP Flag
Timing Capacitor
GND
(Top View)
NOTE:
EP Flag must be tied to GND Pin 4 on PCB
Figure 2. Pin Connections
Figure 3. Pin Connections
NCP3065 8 N.C. SET dominant R Q S 7 Ipk Sense COMPARATOR + 0.2 V 6 +VCC COMPARATOR + 5 Comparator Inverting Input 0.235 V REFERENCE REGULATOR S Q R SET dominant OSCILLATOR CT 3 Timing Capacitor 2 Switch Emitter TSD 1 Switch Collector
4 GND
Figure 4. Block Diagram PIN DESCRIPTION
Pin No. 1 2 3 4 5 6 7 8 Pin Name Switch Collector Switch Emitter Timing Capacitor GND Comparator Inverting Input VCC Ipk Sense N.C. Internal Darlington switch collector Internal Darlington switch emitter Timing Capacitor Oscillator Input, Timing Capacitor Ground pin for all internal circuits Inverting input pin of internal comparator Voltage supply Peak Current Sense Input to monitor the voltage drop across an external resistor to limit the peak current through the circuit Pin not connected Description
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2
C C C C
CC CC CC CC
Switch Collector
1
8
N.C.
N.C. Ipk Sense VCC Comparator Inverting Input
NCP3065, NCV3065
MAXIMUM RATINGS (measured vs. pin 4, unless otherwise noted)
Rating VCC (Pin 6) Comparator Inverting Input (Pin 5) Darlington Switch Collector (Pin 1) Darlington Switch Emitter (Pin 2) (Transistor OFF) Darlington Switch Collector to Emitter (Pins 1-2) Darlington Switch Current Ipk Sense (Pin 7) Timing Capacitor (Pin 3) Power Dissipation and Thermal Characteristics PDIP-8 (Note 5) Thermal Resistance Junction-to-Air SOIC-8 (Note 5) Thermal Resistance Junction-to-Air DFN-8 (Note 5) Thermal Resistance Junction-to-Air Thermal Resistance Junction-to-Case Storage Temperature Range Maximum Junction Temperature Operating Junction Temperature Range (Note 3) NCP3065, NCV3065 C/W RqJA RqJA RqJA RqJC TSTG TJ(MAX) TJ -40 to +125 100 C/W 180 C/W 78 14 -65 to +150 +150 C C C Symbol VCC VCII VSWC VSWE VSWCE ISW VIPK VTCAP Value 0 to +40 -0.2 to +VCC 0 to +40 -0.6 to +VCC 0 to +40 1.5 -0.2 to VCC + 0.2 -0.2 to +1.4 Unit V V V V V A V V
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability. 1. This device series contains ESD protection and exceeds the following tests: Pin 1-8: Human Body Model 2000 V per AEC Q100-002; 003 or JESD22/A114; A115 Machine Model Method 200 V 2. This device contains latch-up protection and exceeds 100 mA per JEDEC Standard JESD78. 3. The relation between junction temperature, ambient temperature and Total Power dissipated in IC is TJ = TA + Rq * PD 4. The pins which are not defined may not be loaded by external signals 5. 1 oz copper, 1 in2 copper area
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NCP3065, NCV3065
ELECTRICAL CHARACTERISTICS (VCC = 5.0 V, TJ = -40C to +125C, unless otherwise specified)
Characteristic OSCILLATOR Frequency Discharge to Charge Current Ratio Capacitor Discharging Current Capacitor Charging Current Current Limit Sense Voltage OUTPUT SWITCH (Note 6) Darlington Switch Collector to Emitter Voltage Drop Collector Off-State Current COMPARATOR Threshold Voltage TJ = 25C TJ = 0 to +85C TJ = -40C to +125C Threshold Voltage Line Regulation Input Bias Current TOTAL DEVICE Supply Current (VCC = 5.0 V to 40 V, CT = 2.2 nF, Pin 7 = VCC, VPin 5 > Vth, Pin 2 = GND, remaining pins open) ICC 7.0 mA (VCC = 3.0 V to 40 V) (Vin = Vth) VTH REGLiNE ICII in -10 -6.0 -1000 -100 VTH 235 5 +10 6.0 1000 mV % % mV nA (ISW = 1.0 A, TJ = 25C) (Note 6) (VCE = 40 V) VSWCE(DROP) IC(OFF) 1.0 0.01 1.3 100 V mA (VPin 5 = 0 V, CT = 2.2 nF, TJ = 25C) (Pin 7 to VCC, TJ = 25C) (Pin 7 to VCC, TJ = 25C) (Pin 7 to VCC, TJ = 25C) (TJ = 25C) (Note 7) fOSC IDISCHG / ICHG IDISCHG ICHG VIPK(Sense) 165 110 5.5 150 6.0 1650 275 185 235 190 6.5 kHz mA mA mV Conditions Symbol Min Typ Max Unit
Thermal Shutdown Threshold Hysteresis
160 10
C C
6. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient temperature as possible. 7. The VIPK(Sense) Current Limit Sense Voltage is specified at static conditions. In dynamic operation the sensed current turn-off value depends on comparator response time and di/dt current slope. See the Operating Description section for details. 8. NCV prefix is for automotive and other applications requiring site and change control.
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NCP3065, NCV3065
450 400 350
FREQUENCY (kHz) FREQUENCY (Hz) 190 180 170 160 150 140 130 120 110 CT = 2.2 nF TJ = 25C
300 250 200 150 100 50 0 0 1 2 3 4 5 6 7 8 9 10 11 12 1314 1516 1718 1920
Ct, CAPACITANCE (nF)
3
7
12
16
21
25
29
34
38 40
VCC, SUPPLY VOLTAGE (V)
Figure 5. Oscillator Frequency vs. Oscillator Timing Capacitor
Figure 6. Oscillator Frequency vs. Supply Voltage
2.4 2.2 VOLTAGE DROP (V) 2.0 1.8 1.6 1.4 1.2 1.0 -50 0 50 100 150 VCC = 5.0 V IE = 1 A VOLTAGE DROP (V)
1.25 VCC = 5.0 V IC = 1 A
1.20
1.15
1.10
1.05 1.0 -50
0
50
100
150
TJ, JUNCTION TEMPERATURE (C)
TJ, JUNCTION TEMPERATURE (C)
Figure 7. Emitter Follower Configuration Output Darlington Switch Voltage Drop vs. Temperature
Figure 8. Common Emitter Configuration Output Darlington Switch Voltage Drop vs. Temperature
2.0 1.9 1.8 VOLTAGE DROP (V) 1.7 1.6 1.5 1.4 1.3 1.2 1.1 1.0 0 0.5 1.0 1.5 IE, EMITTER CURRENT (A) VCC = 5.0 V TJ = 25C VOLTAGE DROP (V)
1.5 1.4 1.3 1.2 1.1 1.0 0.9 0.8 0.7 0.6 0.5 0 0.5 1.0 1.5 IC, COLLECTOR CURRENT (A) VCC = 5.0 V TJ = 25C
Figure 9. Emitter Follower Configuration Output Darlington Switch Voltage Drop vs. Emitter Current
Figure 10. Common Emitter Configuration Output Darlington Switch Voltage Drop vs. Collector Current
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NCP3065, NCV3065
Vth, COMPARATOR THRESHOLD VOLTAGE (V) 0.25 Vipk(sense), CURRENT LIMIT SENSE VOLTAGE (V) 0.30 0.28 0.26 0.24 0.22 0.20 0.18 0.16 0.14 0.12 0.10 -40 -25 -10
0.245 0.24
0.235 0.23
0.225 0.22 -50 -30 -10
10
30
50
70
90
110 130 150
5
20
35
50
65
80
95
110 125
TJ, JUNCTION TEMPERATURE (C)
TJ, JUNCTION TEMPERATURE (C)
Figure 11. Comparator Threshold Voltage vs. Temperature
6.0 ICC, SUPPLY CURRENT (mA) 5.5 5.0 4.5 4.0 3.5 3.0 2.5 2.0 3.0 8.0 13 18 23 28
Figure 12. Current Limit Sense Voltage vs. Temperature
CT = 2.2 nF Pin 5, 7 = VCC Pin 2 = GND 33 38 43
VCC, SUPPLY VOLTAGE (V)
Figure 13. Standby Supply Current vs. Supply Voltage
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NCP3065, NCV3065
INTRODUCTION The NCP3065 is a monolithic power switching regulator optimized for LED Driver applications. Its flexible architecture enables the system designer to directly implement a step-up or step-down topology with a minimum number of external components for driving LEDs. A representative block diagram is shown in Figure 4.
OPERATING DESCRIPTION
comparator value, the output switch cycle is inhibited. When the load current causes the output voltage to fall below the nominal value feedback comparator enables switching immediately. Under these conditions, the output switch conduction can be enabled for a partial oscillator cycle, a partial cycle plus a complete cycle, multiple cycles, or a partial cycle plus multiple cycles.
Oscillator
The NCP3065 operates as a fixed oscillator frequency output voltage ripple gated regulator. In general, this mode of operation is somewhat analogous to a capacitor charge pump and does not require dominant pole loop compensation for converter stability. The typical operating waveforms are shown in Figure 14. The output voltage waveform shown is for a step-down converter with the ripple and phasing exaggerated for clarity. During initial converter startup, the feedback comparator senses that the output voltage level is below nominal. This causes the output switch to turn on and off at a frequency and duty cycle controlled by the oscillator, thus pumping up the output filter capacitor. When the feedback voltage level reaches nominal
The oscillator frequency and off-time of the output switch are programmed by the value of the timing capacitor CT. Capacitor CT is charged and discharged by a 1 to 6 ratio internal current source and sink, generating a positive going sawtooth waveform at Pin 3. This ratio sets the maximum tON/(tON+tOFF) of the switching converter as 6/(6+1) or 85.7% (typical). The oscillator peak and valley voltage difference is 500 mV typically. To calculate the CT capacitor value for required oscillator frequency, use the equations found in Figure 22. An online NCP3065 design tool can be found at www.onsemi.com, which adds in selecting component values.
1 Feedback Comparator Output 0 1 IPK Comparator Output 0
Timing Capacitor, CT
On Output Switch Off
Nominal Output Voltage Level
Output Voltage Startup Operation
Figure 14. Typical Operating Waveforms
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NCP3065, NCV3065
Peak Current Sense Comparator LED Dimming
Under normal conditions, the output switch conduction is initiated by the Voltage Feedback comparator and terminated by the oscillator. Abnormal operating conditions occur when the converter output is overloaded or when feedback voltage sensing is lost. Under these conditions, the Ipk Current Sense comparator will protect the Darlington output Switch. The switch current is converted to a voltage by inserting a fractional ohm resistor, RSC, in series with VCC and the Darlington output switch. The voltage drop across RSC is monitored by the Current Sense comparator. If the voltage drop exceeds 200 mV (nom) with respect to VCC, the comparator will set the latch and terminate the output switch conduction on a cycle-by-cycle basis. This Comparator/Latch configuration ensures that the Output Switch has only a single on-time during a given oscillator cycle.
Real Vturn-off on Rs Resistor di/dt slope Vipk(sense) Io t_delay I1 I through the Darlington Switch
The COMP pin of the NCP3065 is used to provide dimming capability. In digital input mode the PWM input signal inhibits switching of the regulator and reduces the average current through the LEDs. In analog input mode a PWM input signal is RC filtered and the resulting voltage is summed with the feedback voltage thus reduces the average current through the LEDs. Figure 15 illustrated the linearity of the digital dimming function with a 200 Hz digital PWM. For further information on dimming control refer to application note AND8298.
800 24 Vin, Vf = 7.2 V 700 24 Vin, Vf = 3.6 V 600 ILED (mA) 500 12 Vin, Vf = 3.6 V 400 300 200 100 0 0 10 20 30 40 50 60 70 80 90 100 DUTY CYCLE (%)
The VIPK(Sense) Current Limit Sense Voltage threshold is specified at static conditions. In dynamic operation the sensed current turn-off value depends on comparator response time and di/dt current slope. Real Vturn-off on Rsc resistor
Vturn_off + Vipk(sense) ) Rsc @ (t_delay @ di dt)
Figure 15. No Output Capacitor Operation
Typical Ipk comparator response time t_delay is 350 ns. The di/dt current slope is dependent on the voltage difference across the inductor and the value of the inductor. Increasing the value of the inductor will reduce the di/dt slope. It is recommended to verify the actual peak current in the application at worst conditions to be sure that the max peak current will never get over the 1.5 A Darlington Switch Current max rating.
Thermal Shutdown
Internal thermal shutdown circuitry is provided to protect the IC in the event that the maximum junction temperature is exceeded. When activated, typically at 165C, the Darlington Output Switch is disabled. The temperature sensing circuit is designed with some hysteresis. The Darlington Switch is enabled again when the chip temperature decreases under the low threshold. This feature is provided to prevent catastrophic failures from accidental device overheating. It is not intended to be used as a replacement for proper heatsinking.
A constant current buck regulator such as the NCP3065 focuses on the control of the current through the load, not the voltage across it. The switching frequency of the NCP3065 is in the range of 100-300 kHz which is much higher than the human eye can detect. This allows us to relax the ripple current specification to allow higher peak to peak values. This is achieved by configuring the NCP3065 in a continuous conduction buck configuration with low peak to peak ripple thus eliminating the need for an output filter capacitor. The important design parameter is to keep the peak current below the maximum current rating of the LED. Using 15% peak to peak ripple results in a good compromise between achieving max average output current without exceeding the maximum limit. This saves space and reduces part count for applications that require a compact footprint. (Example: See Figure 17) See application note AND8298 for more information.
Output Switch
The output switch is designed in a Darlington configuration. This allows the application designer to operate at all conditions at high switching speed and low voltage drop. The Darlington Output Switch is designed to switch a maximum of 40 V collector to emitter voltage and current up to 1.5 A.
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NCP3065, NCV3065
APPLICATIONS Figures 16 through 24 show the simplicity and flexibility of the NCP3065. Two main converter topologies are demonstrated with actual test data shown below each of the circuit diagrams.
(See Notes 9, 10, 11) Step-Down
Figure 16 gives the relevant design equations for the key parameters. Additionally, a complete application design aid for the NCP3065 can be found at www.onsemi.com.
Step-Up
ton toff ton
Vout ) VF Vin * VSWCE * Vout
ton toff
Vout ) VF * Vin Vin * VSWCE
ton toff
f CT IL(avg) Ipk (Switch) RSC L Vripple(pp) DIL Vout I out
ton toff
)1 CT + 381.6 @ 10 fosc
*6
f * 343 @ 10 *12
ton toff
)1
Iout DI IL(avg) ) L 2 0.20 Ipk (Switch) Vin * VSWCE * Vout ton DIL 1 8 f CO VTH
2
t Iout on ) 1 toff DI IL(avg) ) L 2 0.20 Ipk (Switch) Vin * VSWCE ton DIL tI [ on out ) DIL @ ESR CO VTH R2 )1 R1
) (ESR) 2
R2 )1 R1
V ref R sense
V ref R sense
9. VSWCE - Darlington Switch Collector to Emitter Voltage Drop, refer to Figures 7, 8, 9 and 10. 10. VF - Output rectifier forward voltage drop. Typical value for 1N5819 Schottky barrier rectifier is 0.4 V. 11. The calculated ton/toff must not exceed the minimum guaranteed oscillator charge to discharge ratio.
The Following Converter Characteristics Must Be Chosen:
Vin - Nominal operating input voltage. Vout - Desired output voltage. Iout - Desired output current. DIL - Desired peak-to-peak inductor ripple current. For maximum output current it is suggested that DIL be chosen to be less than 10% of the average inductor current IL(avg). This will help prevent Ipk (Switch) from reaching the current limit threshold set by RSC. If the design goal is to use a minimum inductance value, let DIL = 2(IL(avg)). This will proportionally reduce converter output current capability. f - Maximum output switch frequency. Vripple(pp) - Desired peak-to-peak output ripple voltage. For best performance the ripple voltage should be kept to a low value since it will directly affect line and load regulation. Capacitor CO should be a low equivalent series resistance (ESR) electrolytic designed for switching regulator applications.
Figure 16. Design Equations
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NCP3065, NCV3065
NTF2955 Q4 MMBT3904LT1G Q5 R15 1k R6 R7 U1 8 N.C. SWC 1 7 SWE 2 IPK 6 3 VCC TCAP 5 COMP GND 4 NCP3065 SOIC8 MMSD4148 D2 L1 CT C3 1.8 nF R8 15 k D1 MBRS140LT3G C5 R9 BC807-LT1G Q1 J6 1 ON/OFF R11 BC817-LT1G Q2 10 k R13 NU R14 NU 0805 100 pF J5 1 R12 RSENSE 1% -LED J7 1 GND 470 mH C1 1208 0.1 mF + J1 1 +LED C6 NU
6x 1R0 1%R 0R10 R1 J2 1 +VIN C4 J3 1 GND J4 1 +VAUX 0.1 mF + C2 220 mF / 50 V R2 R3 R4 R5
1206 1206 1206 1206 1206 1206 1206
R10 1k
Figure 17. Buck Demo Board with External Switch Application Schematic
This design illustrates the NCP3065 being used as a PFET controller, the design has been optimized for continuous current operation with low ripple which allows the output filter capacitor to be eliminated. Figure 20 illustrates the
Value of Components
Name C1, C4 C2 C3 C5 D1 D2 L1 Q4 Value 100 nF, Ceramic Capacitor, 1206 220 mF, 50 V, Electrolytic Capacitor 1.8 nF, Ceramic Capacitor, 0805 100 pF, Ceramic Capacitor, 0805 1 A, 40 V Schottky Rectifier MMSD4148 470 mH, DO5022P-474ML Coilcraft Inductor NTF2955, P-MOSFET, SOT223
efficiency with 1 and 2 LEDs and output currents of 350 mA and 700 mA. Additional data and design information can be found of this design in Application Note AND8298.
Name Q5 R1 R8 R9 R10, R15 R11 R12 U1
Value MMBT3904LT1G, SOT23 100 mW, 0.5 W 15 k, resistor 0805 10 kW, resistor 0805 1 kW, resistor 0805 1.2 kW, resistor 0805 RSENSE 1%, 1206 NCP3065, SOIC8
NOTE: RSENSE is used to select LED output current, for 350 mA use 680 mW, for 700 mA use 330 mW and for 1000 mA use 220 mW
Test Results (without output capacitor)
Test Line Regulation Load Regulation Output Ripple Efficiency Condition Vin = 9 V to 35 V, Io = 350 mA Vin = 12 V, Io = 350 mA, Vo = 3 V to 8 V Vin = 9 V to 35 V, Io = 350 mA Vin = 12 V, Io = 350 mA, VOUT = 3 to 8 V 12 mA 13 mA < 15% IO > 75% Results
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NCP3065, NCV3065
88 84 VOUT = 7.2 V, No Output Cap EFFICIENCY (%) 80 76 72 68 VOUT = 3.6 V, No Output Cap 64 60 4 8 12 16 20 24 28 32 36 VIN, INPUT VOLTAGE (V)
Figure 18. 1.5 A Buck Demoboard Layout
Figure 19. Efficiency vs. Input Voltage for the 1.5 A Buck Demo Board at Iout = 700 mA, TA = 255C, Without Output Capacitor
88 84 80 EFFICIENCY (%) 76 72 68 64 60 56 4 8 12 16 20 24 28 32 36 VIN, INPUT VOLTAGE (V) VOUT = 3.6 V, Output Cap 100 mF EFFICIENCY (%) VOUT = 7.2 V, Output Cap 100 mF
88 VOUT = 7.2 V, Output Cap 100 mF 84 80 76 72 VOUT = 3.6 V, Output Cap 100 mF 68 64 60 4 8 12 16 20 24 28 32 36 VIN, INPUT VOLTAGE (V)
Figure 20. Efficiency vs. Input Voltage for the 1.5 A Buck Demo Board at Iout = 350 mA, TA = 255C, with 100 mF Output Capacitor
Figure 21. Efficiency vs. Input Voltage for the 1.5 A Buck Demo Board at Iout = 700 mA, TA = 255C, with 100 mF Output Capacitor
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NCP3065, NCV3065
L1 0R15 R1 J2 1 +VIN J4 1 GND C5 0.1 mF + C3 220 mF / 50 V R2 6x 1R0 1%R R3 R4 R5 R6 R7 100 mH U1 8 N.C. SWC 7 SWE IPK 6 VCC TCAP 5 COMP GND NCP3065 R8 1k0 J6 1 +VAUX J5 1 R9 -LED RSENSE D2 BC807-LT1G Q1 R10 1 ON/OFF 1k2 J7 Q2 R11 NU MM3Z36VT1G MBRS140LT3G 1 2 3 4 C4 2.2 nF D1 C2 0.1 mF + C1 100 mF / 50 V J1 1 +VOUT
J3 1 GND
BC817-LT1G
Figure 22. Boost Demo Board Application Schematic
Value of Components
Name C1 C2, C5 C3 C4 D1 D2 L1 Value 100 mF/50 V, Electrolytic Capacitor 100 nF, Ceramic Capacitor, 1206 220 mF/50 V, Electrolytic Capacitor 2.2 nF, Ceramic Capacitor, 0805 MBRS140LT3G, Schottky diode MMSZ36VT1G, Zener diode 100 mH, DO3340P-104ML Coilcraft Inductor Name Q2 R1 R8 R9 R10 U1 Value BC817-LT1G, SOT23 150 mW, resistor 0.5 W 1 k, resistor 0805 Load current sense resistor, 1206 1.2 k, resistor 0805 NCP3065, SOIC8
Test Results
Test Line Regulation Output Ripple Efficiency Condition Vin = 10 V to 20 V, Vo = 22 V, IOAVG = 350 mA Vin = 8 V to 20 V, Vo = 22 V, IOAVG = 350 mA Vin = 10 to 20 V, IOAVG = 350 mA 25 mA 50 mA > 83 % Results
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NCP3065, NCV3065
95 93 91 EFFICIENCY (%) 89 87 85 83 81 79 77 75 8 10 12 14 16 18 20 22 VIN, INPUT VOLTAGE (V)
Figure 23. Boost Demoboard Layout
Figure 24. Efficiency vs. Input Voltage for the Boost Demo Board at IOUT = 350 mA, VOUT = 22 V (6xLED with VF = 3.6 V), TA = 255C
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NCP3065, NCV3065
MTB30P06V Q4 MMBT3904LT1G Q5 R15 1k R6 R7 U1 8 N.C. SWC 1 7 SWE 2 IPK 6 3 VCC TCAP 5 COMP GND 4 NCP3065 SOIC8 C8 0.1 mF R9 BC807-LT1G Q1 R11 1 1k2 ON/OFF 0805 J6 Q2 10 k 0805 C5 R14 NU 0805 R13 NU MMSD4148 D2 PF0504.223NL CT C3 1.8 nF R8 15 k L1 C1 1206 0.1 mF D1 J1 1 +LED +
6x 1R0 1%R 0R04 R1 J2 1 +VIN C4 J3 1 GND J4 1 +VAUX 0.1 mF + C7 + 1 mF / 50 V R2 R3 R4 R5
1206 1206 1206 1206 1206 1206
C2 220 mF / 50 V
C6
MBRS140LT3G 100 pF
220 mF / 50 V J5 1
R10 1k R16 0R15 1% R12 0R15 1%
-LED J7 1 GND
BC817-LT1G
Figure 25. Buck Demoboard with External Switch Application Schematic
Value of Components
Name C1 C1, C4, C8 C2, C6 C3 C5 C7 D1 D2 L1 Q2 Value 100 mF, 50 V, Electrolytic Capacitor 100 nF, Ceramic Capacitor, 1206 220 mF, 50 V, Electrolytic Capacitor 2.2 nF, Ceramic Capacitor, 0805 100 pF, Ceramic Capacitor, 0805 1 mF / 50 V, Ceramic Capacitor, 1206 MBRS540LT3G, Schottky Diode MMSD4148T1G, Diode 22 mH BC817-LT1G, SOT23 Name Q4 Q5 R1 R8 R9 R10 R11 R12, R16 U1 Value MTB30P06V, P-MOS transistor MMBT3904LT1G 40 mW, Resistor 0.5 W 6k8, Resistor 0805 10k, Resistor 0805 1k, Resistor 0805 1k2, Resistor 0805 150 mW, Resistor 0.5 W NCP3065, SOIC8
Test Results
Test Line Regulation Output Ripple Efficiency Short Circuit Current Condition Vin = 8 V to 35 V, Io = 3000 mA Vin = 12 V, Io = 3000 mA Vin = 12 V, Io = 3000 mA Vin = 12 V, Rload = 0.15 W < 6% < 6% > 78% Results
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NCP3065, NCV3065
90 88 86 84 82 80 78 76 74 72 70 68 66 8 10 12 14 16 18 20 22 24 26 28 30 32 34 36 VIN, INPUT VOLTAGE (v)
EFFICIENCY (%)
Figure 26. 3 A Buck Demoboard Layout
Figure 27. Efficiency vs. Input Voltage for the 3 A Buck Demo Board at IOUT = 3 A, VOUT = 4 V, TA = 255C
ORDERING INFORMATION
Device NCP3065MNTXG NCP3065PG NCP3065DR2G NCV3065MNTXG NCV3065PG NCV3065DR2G Package DFN-8 (Pb-Free) PDIP-8 (Pb-Free) SOIC-8 (Pb-Free) DFN-8 (Pb-Free) PDIP-8 (Pb-Free) SOIC-8 (Pb-Free) Shipping 4000 Units / Tape & Reel 50 Units / Rail 2500 Units / Tape & Reel 4000 Units / Tape & Reel 50 Units / Rail 2500 Units / Tape & Reel
For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging Specifications Brochure, BRD8011/D.
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NCP3065, NCV3065
PACKAGE DIMENSIONS
8 LEAD PDIP CASE 626-05 ISSUE L
8 5
-B1 4
NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. DIM A B C D F G H J K L M N MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC --10_ 0.76 1.01 AC IN DC + IN DC - IN AC IN GROUND OUTPUT AUXILIARY VCC INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC --10_ 0.030 0.040
F
NOTE 2
-AL
C -TSEATING PLANE
J N D K
M
M
H
G 0.13 (0.005) TA
M
B
M
STYLE 1: PIN 1. 2. 3. 4. 5. 6. 7. 8.
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NCP3065, NCV3065
PACKAGE DIMENSIONS
SOIC-8 NB CASE 751-07 ISSUE AH
-XA
8 5
B
1 4
S
0.25 (0.010)
M
Y
M
-YG C -ZH D 0.25 (0.010)
M SEATING PLANE
K
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. 6. 751-01 THRU 751-06 ARE OBSOLETE. NEW STANDARD IS 751-07. MILLIMETERS MIN MAX 4.80 5.00 3.80 4.00 1.35 1.75 0.33 0.51 1.27 BSC 0.10 0.25 0.19 0.25 0.40 1.27 0_ 8_ 0.25 0.50 5.80 6.20 INCHES MIN MAX 0.189 0.197 0.150 0.157 0.053 0.069 0.013 0.020 0.050 BSC 0.004 0.010 0.007 0.010 0.016 0.050 0_ 8_ 0.010 0.020 0.228 0.244
N
X 45 _
0.10 (0.004) M ZY
S
J
X
S
DIM A B C D G H J K M N S
SOLDERING FOOTPRINT*
1.52 0.060
7.0 0.275
4.0 0.155
0.6 0.024
1.270 0.050
SCALE 6:1 mm inches
*For additional information on our Pb-Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.
http://onsemi.com
17
NCP3065, NCV3065
PACKAGE DIMENSIONS
8 PIN DFN, 4x4 CASE 488AF-01 ISSUE B
NOTES: 1. DIMENSIONS AND TOLERANCING PER ASME Y14.5M, 1994. 2. CONTROLLING DIMENSION: MILLIMETERS. 3. DIMENSION b APPLIES TO PLATED TERMINAL AND IS MEASURED BETWEEN 0.25 AND 0.30 MM FROM TERMINAL. 4. COPLANARITY APPLIES TO THE EXPOSED PAD AS WELL AS THE TERMINALS. MILLIMETERS MIN MAX 0.80 1.00 0.00 0.05 0.20 REF 0.25 0.35 4.00 BSC 1.91 2.21 4.00 BSC 2.09 2.39 0.80 BSC 0.20 --0.30 0.50
D
PIN ONE IDENTIFICATION
A
8X
L
1
B
8X
K
E
2X
0.15 C b
2X 8X NOTE 3
0.15 C
TOP VIEW
0.10 C A B 0.05 C
0.10 C
8X
A
0.08 C
SEATING PLANE
A1
(A3)
SIDE VIEW
C
SOLDERING FOOTPRINT*
4.30 2.21
8X
1
8X
0.35
DIMENSIONS: MILLIMETERS
*For additional information on our Pb-Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.
ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. "Typical" parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT: Literature Distribution Center for ON Semiconductor P.O. Box 5163, Denver, Colorado 80217 USA Phone: 303-675-2175 or 800-344-3860 Toll Free USA/Canada Fax: 303-675-2176 or 800-344-3867 Toll Free USA/Canada Email: orderlit@onsemi.com N. American Technical Support: 800-282-9855 Toll Free USA/Canada Europe, Middle East and Africa Technical Support: Phone: 421 33 790 2910 Japan Customer Focus Center Phone: 81-3-5773-3850 ON Semiconductor Website: www.onsemi.com Order Literature: http://www.onsemi.com/orderlit For additional information, please contact your local Sales Representative
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18
CC CC CC CC CC CC CC CC
C CC C CC C CC C CC C CC
8 5
D2
4
E2
e
BOTTOM VIEW
DIM A A1 A3 b D D2 E E2 e K L
CC CC CC CC CC CC CC CC
CC C CC CC C CC
2.39
0.63
0.40 0.80 PITCH
2.75
NCP3065/D

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